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dual precision, rail-to-rail output operational amplifier ad8698 rev. 0 information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent ri ghts of analog devices. trademarks and registered trademarks are the prop erty of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.326.8703 ? 2004 analog devices, inc. all rights reserved. features low offset voltage: 100 v max low offset voltage drift: 2 v/c max low input bias current: 700 pa max low noise: 8 nv/ hz high common-mode rejection: 118 db min wide operating temperature: ? 40c to +85c no phase reversal applications photodiode amplifier sensors and controls multipole filters integrator general description the ad8698 is a high precision, ra il-to-rail output, low noise, low input bias current operational amplifier. offset voltage is a respectable 100 v max and drift over temperature is below 2 v/c, eliminating the need for manual offset trimming. the ad8698 is ideal for high impedanc e sensors, minimizing offset errors due to input bias and offset currents. the rail-to-rail output maximizes dynamic range in a variety of applications, such as photodiode amplifiers, dac i/v amplifiers, filters, and adc input amplifiers. the ad8698 dual amplifiers are offered in 8-lead msop and narrow 8-lead soic packages. the msop version is available in tape and reel only. connection diagrams 8-lead soic (r-8) out a 1 ?in a 2 +in a 3 v? 4 v+ 8 out b 7 ?in b 6 +in b 5 ad8698 top view (not to scale) 04807-0-069 8-lead msop (rm-8) out a 1 ?in a 2 +in a 3 v? 4 v+ 8 out b 7 ?in b 6 +in b 5 ad8698 top view (not to scale) 04807-0-070 figure 1.
ad8698 rev. 0 | page 2 of 20 table of contents specifications .................................................................................... 3 absolute maximum ratings ........................................................... 5 thermal resistance ...................................................................... 5 esd caution.................................................................................. 5 typical performance characteristics............................................. 6 applications .................................................................................... 14 input overvoltage protection................................................... 14 driving capacitive loads .......................................................... 14 instrumentation amplifier ....................................................... 15 composite amplifier ................................................................. 15 low noise applications ............................................................ 16 driving adcs ............................................................................. 16 using the ad8698 in active filt er designs ........................... 16 outline dimensions....................................................................... 17 ordering guide .......................................................................... 17 revision history 4/04revision 0: initial version
ad8698 rev. 0 | page 3 of 20 specifications v s = 15 v, v cm = 0 v (@t a = 25 o c, unless otherwise noted.) table 1. parameter symbol conditions min typ max unit input characteristics offset voltage v os 20 100 v ? 40c < t a < +85c 300 v offset voltage drift ? v os / ? t ? 40c < t a < +85c 0.6 2 v/c input bias current i b 700 pa ? 40c < t a < +85c 1500 pa input offset current i os 700 pa ? 40c < t a < +85c 1500 pa input voltage range ivr ? 40c < t a < +85c ? 13.5v 13.5 v common-mode rejection ratio cmrr v cm = 13.5 v 118 132 db large signal voltage gain a vo r l = 2 k ? , v o = 13.5 v 900 1450 v/mv input capacitance c diff 6.5 pf c cm 4.6 pf output characteristics output voltage swing (ref. to gnd) v oh i l = 1 ma, ? 40c < t a < +85c 14.85 14.93 v v oh i l = 5 ma, ? 40c < t a < +85c 14.6 14.8 v (ref. to gnd) v ol i l = 1 ma, ? 40c < t a < +85c ? 14.93 ? 14.6 v v ol i l = 5 ma, ? 40c < t a < +85c ? 14.82 ? 14.5 v power supply power supply rejection ratio psrr 2.5 v < v s < 15 v 114 132 db supply current i sy v o = 0 v 2.8 3.2 ma ? 40c < t a < +85c 3.8 ma supply voltage v s ? 40c < t a < +85c 2.5 15 v dynamic performance slew rate sr r l = 2 k ? 0.4 v/s gain bandwidth product gbp 1 mhz phase margin ? o 60 degrees noise performance input noise voltage e n p-p 0.1 hz < f < 10 hz 0.6 v p-p input voltage noise density e n f = 10 hz 15 nv/ hz input voltage noise density e n f = 1 khz 8 nv/ hz current noise density i n f = 1 khz 0.2 pa/ hz
ad8698 rev. 0 | page 4 of 20 v s = 2.5 v, v cm = 0 v (@t a = 25 o c, unless otherwise noted.) table 2. parameter symbol conditions min typ max unit input characteristics offset voltage v os 20 100 v ? 40c < t a < +85c 300 v offset voltage drift ? v os / ? t ? 40c < t a < +85c 2 v/c input bias current i b 700 pa ? 40c < t a < +85c 1500 pa input offset current i os 700 pa ? 40c < t a < +85c 1500 pa input voltage range ivr ? 40c < t a < +85c ? 1.5 +1.5 v common-mode rejection ratio cmrr v cm = 13.5 v 105 120 db large signal voltage gain a vo r l = 2 k ? , v o = 13.5 v 600 1200 v/mv input capacitance c diff 6.4 pf c cm 4.6 pf output characteristics output voltage swing (ref. to gnd) v oh i l = 1 ma, ? 40c < t a < +85c 2.35 2.44 v v oh i l = 5 ma, ? 40c < t a < +85c 2.1 2.29 v (ref. to gnd) v ol i l = 1 ma, ? 40c < t a < +85c ? 2.43 ? 2.2 v v ol i l = 5 ma, t a = 25c ? 2.15 ? 1.9 v i l = 5ma, ? 40c ad8698 rev. 0 | page 5 of 20 absolute maximum ratings table 3. parameter rating supply voltage 15 v input voltage v s differential input voltage v s output short-circuit duration to gnd indefinite storage temperature range r, rm packages ? 65c to +150c operating temperature range ? 40c to +85c junction temperature range r, rm packages ? 65c to +150c lead temperature range (soldering, 60 sec) +300c stresses above those listed u nder absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is no t implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. thermal resistance ja is specified for the worst-case conditions, i.e., ja is specified for devices soldered in circuit boards for surface-mount packages. table 4. thermal resistance package type ja jc unit msop-8 (rm) 210 45 c/w soic-8 (r) 158 43 c/w esd caution esd (electrostatic discharge) sensitive device. electrosta tic charges as high as 1000 v readily accumulate on the human body and test equipment and can discharge with out detection. although this product features proprietary esd protection circuitry, permanent dama ge may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality.
ad8698 rev. 0 | page 6 of 20 typical performance characteristics 0 10 20 30 40 50 number of amplifiers 60 70 80 0 0.2 0.4 0.6 0.8 1.0 1.2 tcv os ( v/c) 04807-0-034 v s = 15v figure 2. input offset voltage drift distribution 0 10 20 30 40 50 number of amplifiers 60 70 80 ?100 ?80 ?60 ?40 ?20 0 40 80 20 60 100 v os ( v) 04807-0-058 v s = 15v figure 3. offset voltage distribution 0 10 20 30 40 50 60 70 number of amplifiers ?400 ?320 ?240 ?160 ?80 0 160 320 80 240 400 i b (pa) 04807-0-060 v s = 15v figure 4. input bias distribution ?40 ?20 0 20 40 60 80 100 gain (db) ?90 ?45 0 45 90 135 180 225 phase margin (degrees) frequency (hz) 10k 1m 100k 10m 04807-0-001 v s = 15v figure 5. open-loop gain and phase vs. frequency ?20 ?10 0 10 20 30 40 50 closed-loop gain (db) frequency (hz) 10k 1k 100k 1m 10m 04807-0-009 v s = 15v a v = 100 a v = 1 a v = 10 figure 6. closed-loop gain vs. frequency output impedance ( ? ) 0 15 30 45 60 10 100 1k 10k 100k 1m frequency (hz) 04807-0-007 v s = 15v a v = 100 a v = 1 a v = 10 figure 7. output impedance vs. frequency
ad8698 rev. 0 | page 7 of 20 voltage (1v/div) v s = 15v v in = 4v p-p c l = 1nf time (100 s/div) 04807-0-037 figure 8. large signal transient response voltage (100mv/div) v s = 15v v in = 200mv p-p c l = 1nf time (100 s/div) 04807-0-044 figure 9. small signal transient response 0 10 20 30 50 overshoot (%) v s = 15v v in = 200mv a v = 1 1000 1500 0 500 2000 2500 3000 capacitive load (pf) 04807-0-013 figure 10. overshoot vs. load capacitance v s = 15v v in = 200mv p-p a v = ?100 voltage (v) voltage (mv) v in ?200 0 0 15 v out time (10 s/div) 04807-0-041 figure 11. positive overvoltage recovery v s = 15v v in = 200mv a v = ?100 time (400 s/div) 04807-0-040 voltage (v) voltage (mv) v in 0 200 ?15 0 v out figure 12. negative overvoltage recovery 0 20 40 60 80 100 120 cmrr (db) frequency (hz) 10k 1k 100k 1m 10m 04807-0-003 v s = 15v figure 13. cmrr vs. frequency
ad8698 rev. 0 | page 8 of 20 0 20 40 60 80 100 10 100 1k 10k 100k 1m frequency (hz) 04807-0-005 v s = 15v +psrr ?psrr figure 14. psrr vs. frequency voltage (200nv/div) v s = 15v time (1s/div) 04807-0-035 figure 15. input voltage noise 1 10 100 voltage noise density (nv/ hz) frequency (hz) 1 0.1 10 100 1k 04807-0-032 v s = 15v figure 16. voltage noise density vs. frequency 0.1 10 1 100 frequency (hz) 1 0.1 10 100 1k 04807-0-033 v s = 15v current noise density (nv/ hz) figure 17. current noise density vs. frequency ?40 ?30 ?20 ?10 0 10 20 short-circuit current (ma) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-030 v s = 15v +i sc ?i sc figure 18. short-circuit current vs. temperature 14.87 14.88 14.89 14.90 14.91 14.92 14.93 14.94 14.95 14.96 output swing (v) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-019 v s = 15v i l = 1ma v oh ?v ol figure 19. output swing vs. temperature
ad8698 rev. 0 | page 9 of 20 14.60 14.65 14.70 14.75 14.80 14.85 14.90 output voltage swing (v) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-020 v s = 15v i l = 5ma v oh ?v ol figure 20. output voltage swing vs. temperature ?30 ?20 ?10 0 10 20 30 ? offset voltage ( v) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-023 v s = 15v figure 21. ? offset voltage vs. temperature 120 125 130 135 140 145 150 155 cmrr (db) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-027 v s = 15v figure 22. cmrr vs. temperature 130 132 134 136 138 140 psrr (db) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-029 v s = 15v figure 23. psrr vs. temperature ? input bias current (pa) ?100 ?50 0 50 100 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-025 v s = 15v figure 24. ? input bias current vs. temperature 0 1 2 3 4 5 6 ? output swing (v) load current (ma) 5 0101520 04807-0-015 v s = 15v v ol v oh figure 25. ? output voltage swing from rails vs. load current
ad8698 rev. 0 | page 10 of 20 supply current (ma) 1.5 2.0 2.5 3.0 3.5 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-017 v s = 15v figure 26. supply current vs. temperature ?140 ?120 ?100 ?80 ?60 ?40 ?20 0 channel separation (db) frequency (hz) 10k 1k 100k 1m 10m 04807-0-010 v s = 15v figure 27. channel separation 0 10 20 30 40 50 60 70 number of amplifiers ?100 ?80 ?60 ?40 ?20 0 40 80 20 60 100 v os ( v) 04807-0-059 v s = 2.5v figure 28. offset voltage distribution ?40 ?20 0 20 40 60 80 100 gain (db) ?90 ?45 0 45 90 135 180 225 phase margin (degrees) frequency (hz) 10k 1m 100k 10m 04807-0-002 v s = 2.5v figure 29. open-loop gain and phase vs. frequency output impedance ( ? ) 0 15 30 45 60 10 100 1k 10k 100k 1m frequency (hz) 04807-0-008 v s = 2.5v a v = 100 a v = 1 a v = 10 figure 30. output impedance vs. frequency voltage (500mv/div) v s = 2.5v v in = 2v p-p c l = 1nf 0 time (100 s/div) 04807-0-038 figure 31. large signal transient response
ad8698 rev. 0 | page 11 of 20 voltage (100mv/div) v s = 2.5v v in = 200mv p-p c l = 1nf time (100 s/div) 04807-0-045 figure 32. small signal transient response 0 10 20 30 40 50 overshoot (%) v s = 2.5v v in = 200mv a v = 1 1000 1500 0 500 2000 2500 3000 capacitive load (pf) 04807-0-014 figure 33. overshoot vs. load capacitance v s = 2.5v v in = 200mv p-p a v = ?100 time (4 s/div) 04807-0-043 voltage (v) voltage (mv) v in ?200 0 0 2.5 v out figure 34. positive overvoltage recovery v s = 2.5v v in = 200mv p-p a v = ?100 time (4 s/div) 04807-0-042 voltage (v) voltage (mv) v in 0 200 ?2.5 0 v out figure 35. negative overvoltage recovery 0 20 40 60 80 100 120 cmrr (db) frequency (hz) 10k 1k 100k 1m 10m 04807-0-004 v s = 2.5v figure 36. cmrr vs. frequency 0 20 40 60 80 100 psrr (db) 10 100 1k 10k 100k 1m frequency (hz) 04807-0-006 v s = 2.5v +psrr ?psrr figure 37. psrr vs. frequency
ad8698 rev. 0 | page 12 of 20 ?30 ?20 ?10 0 10 20 short-circuit current (ma) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-031 v s = 2.5v +i sc ?i sc figure 38. short-circuit current vs. temperature 2.38 2.39 2.40 2.41 2.42 2.43 output voltage (v) 2.44 2.45 2.46 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-021 v s = 2.5v i l = 1ma v oh ?v ol figure 39. output swing vs. temperature 1.5 1.7 1.9 2.1 2.3 2.5 output voltage swing (v) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-022 v s = 2.5v i l = 5ma v oh ?v ol figure 40. output voltage swing vs. temperature ?30 ?20 ?10 0 10 20 30 ? offset voltage ( v) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-024 v s = 2.5v figure 41. ? offset voltage vs. temperature 124 126 128 130 132 134 cmrr (db) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-028 v s = 2.5v figure 42. cmrr vs. temperature ?80 ?70 ?60 ?50 ?40 ?30 ?20 ? input offset current (pa) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-026 v s = 2.5v figure 43. ? input bias current vs. temperature
ad8698 rev. 0 | page 13 of 20 0 500 1000 1500 2000 2500 ? output swing (mv) load current (ma) 5 0101520 04807-0-016 v s = 2.5v v oh v ol figure 44. ? output voltage swing from rails vs. load current 0 0.5 1.0 1.5 2.0 2.5 3.0 supply current (ma) 20 0 ?40 ?20 ?60 40 60 80 100 temperature (c) 04807-0-018 v s = 2.5v figure 45. supply current vs. temperature voltage (2v/div) v s = 5v v in = 11.4v p-p time (400 s/div) 04807-0-039 figure 46. no phase reversal 0 0.5 1.0 1.5 2.0 2.5 3.0 supply current (ma) 0 5 10 15 20 25 30 35 supply voltage (v) 04807-0-012 figure 47. supply current vs. supply voltage ?140 ?120 ?100 ?80 ?60 ?40 ?20 0 channel separation (db) frequency (hz) 10k 1k 100k 1m 10m 04807-0-011 v s = 2.5v figure 48. channel separation
ad8698 rev. 0 | page 14 of 20 applications input overvoltage protection the ad8698 has internal protecti ve circuitry which allows voltages at either input to exceed the supply voltage. however, if voltages applied at either in put exceed the supply voltage by more than 2 v, it is recommended to use a resistor in series with the inputs to limit the input current and prevent damaging the device. the value of the resistor can be calculated from the following formula: ma 5 500 + ? s s in r v v driving capacitive loads the ad8698 is stable even when driving heavy capacitive loads in any configuration. although the ad8698 will safely drive capacitive loads well over 10 nf, it is recommended to use external compensation should the amplifier be subjected to driving a load exceeding 50 nf. this is particularly important in positive unity gain configurations, the worst case for stability. figure 49 shows the output of the ad8698 with a 68 nf load in response to a 400 mv signal at its positive input; the overshoot is less than 25% without any external compensation. using a simple snubber network reduces the overshoot to less than 10% as shown in figure 50. voltage (100mv/div) v s = 15v c l = 68nf a v = 1 time (10 s/div) 04807-0-057. figure 49. heavy capacitive load drive without compensation voltage (100mv/div) v s = 15v c l = 68nf r s = 30 ? c s = 5nf a v = 1 time (10 s/div) 04807-0-061 figure 50. compensated capaciti ve load drive with snubber the snubber network consists of a simple rc network whose values are determined empirically. v+ r s c s c l v? 400mv + ? 04807-0-063 figure 51. snubber network table 5 provides a few starting values for optimum compensation. table 5. compensation values c l (nf) r s ( ? ) c s (nf) 47 20 7 68 30 5 100 50 3 the use of the snubber network does not recover the loss of bandwidth incurred by the lo ad capacitance. the ad8698 maintains a unity gain bandwidth of 1 mhz with load capacitances of up to 1 nf.
ad8698 rev. 0 | page 15 of 20 unity gain bandwidth (mhz) 1k 10k 100k 1m 10m load capacitance (nf) 1 10 100 04807-0-062 figure 52. unity gain bandwidth vs. load capacitance figure 52 shows the unity gain bandwidth as a function of load capacitance. instrumentation amplifier instrumentation amplifiers are used in applications requiring precision, accuracy, and high cmrr. one popular application is signal conditioning in process control, test automation, and measurement instrumentation, wh ere the amplifier is used to amplify small signals. the triple op amp implementa tion uses the ad8698 at the front end with the op184 for optimum accuracy. the circuit in figure 53 enjoys a high overall gain, excellent dc performance, high cmrr, as well as the benefit of an output that swings to the supplies. the cmrr of the in-amp will be limited by the choice of resistor tolerance. r5 is an optional potentiometer that can be used to calibrate the circuit for maximum gain. r7 can be trimmed for optimum cmrr. the output voltage is given by: ? ? ? ? ? ? ? ? ? ? ? ? + = 1 r 2 r 4 r 3 r v v in o 2 1 v? v+ v+ r3 9k ? r1 1k ? r2 10k ? r1 9.8k ? r7 400 ? r4 2k ? r5 10k ? r3 9k ? v? v 2 v 1 04807-0-064 v? v+ op184 1/2 ad8698 1/2 ad8698 figure 53. three op amp in-amp composite amplifier the dc accuracy of the ad8698 and the ac performance of the op184 are combined in the circ uit shown in figure 54. the composite amplifier provides a higher bandwidth, a lower offset voltage, and a higher loop, thereby reducing the gain error substantially. the circuit shown exhibits a total output rms noise of less than 500 v, corresponding to less than 3 mv of peak-to-peak noise over approximately a 3 mhz bandwi dth. cf is used to minimize peaking. the circuit has an inverting gain of 10. in applications with higher closed-loop gains, cf is necessary to maintain a sufficient phase margin and ensure stability. this results in a narrower closed-loop bandwidth. v+ op184 1/2 ad8698 v? v+ v? 04807-0-065 r2 10k ? r1 1k ? cf 20pf v in figure 54. composite amplifier circuit
ad8698 rev. 0 | page 16 of 20 low noise applications in some applications, it is critical to minimize the noise, and although the ad8698 has a low noise of typically 8 nv/ hz at 1 khz, paralleling the two amplifiers within the same package reduces the total noise referred to the input to approximately 5.5 nv/ hz. this simple technique is depicted in figure 55. v? v+ v+ r4 10k ? v? 04807-0-066 r2 10k ? v out v in r3 1k ? r1 1k ? r5 100 ? r3 100 ? figure 55. paralleling amplifiers driving adcs the ad8698 can drive extremel y heavy capacitive loads without any compensation. sometimes capacitors are placed at the output of the amplifier to absorb transient currents while the op amp is interfaced with the adc. most op amps need a small resistor with the output to isolate the load capacitance. this results in a loss of bandwidth and slows the amplifier down substantially. however, the ad8698 maintains a unity gain bandwidth of 1 mhz with loads of up to 1 nf, as shown in figure 52. using the ad8698 in active filter designs the ad8698 is recommended for unit y gain filter designs with a corner frequency of up to 100 khz, one tenth of the op amps unity gain bandwidth. if a higher gain is desired, the corner frequency should be chosen accordingly. for example, if the amplifier is configured with a gain of 10, the corner frequency of the filter should not be more than 10 khz. an example of an active filter is the sallen key. this topology gives the user the flexibility of implementing a low-pass or a high-pass filter by simply inter changing the resistors and the capacitors. in the high-pass filter of figure 56, the damping factor q is set to 1/ 2 for a maximally flat response (butterworth). the gain is unity and the bandwi dth is 10 khz with the values shown. v? v+ 04807-0-067 r2 22k ? r1 11k ? c1 1nf c2 1nf v in figure 56. two pole high-pass filter v? v+ 04807-0-068 r2 11k ? r1 11k ? c1 2nf c2 1nf v in figure 57. two pole low-pass filter the circuit of figure 57 has a bandwidth of 10 khz and a maximally flat response. in this case, the damping factor is controlled by the ratio of the capa citors and the gain is unity.
ad8698 rev. 0 | page 17 of 20 outline dimensions 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) 0.50 (0.0196) 0.25 (0.0099) 45 8 0 1.75 (0.0688) 1.35 (0.0532) seating plane 0.25 (0.0098) 0.10 (0.0040) 4 1 85 5.00 (0.1968) 4.80 (0.1890) 4.00 (0.1574) 3.80 (0.1497) 1.27 (0.0500) bsc 6.20 (0.2440) 5.80 (0.2284) 0.51 (0.0201) 0.31 (0.0122) coplanarit y 0.10 controlling dimensions are in millimeters; inch dimensions (in parentheses) are rounded-off millimeter equivalents for reference only and are not appropriate for use in design compliant to jedec standards ms-012aa figure 58. 8-lead small outline ic [soic] (r-8)dimensions shown in millimeters 0.80 0.60 0.40 8 0 4 85 4.90 bsc pin 1 0.65 bsc 3.00 bsc seating plane 0.15 0.00 0.38 0.22 1.10 max 3.00 bsc coplanarity 0.10 0.23 0.08 compliant to jedec standards mo-187aa figure 59. 8-lead small outline ic [soic] (rm-8)dimensions shown in millimeters ordering guide model temperature package package desc ription package option branding ad8698arm-r2 C40c to +85c msop rm-8 a02 ad8698arm-reel C40c to +85c msop rm-8 a02 ad8698ar C40c to +85c soic r-8 ad8698ar-reel C40c to +85c soic r-8 AD8698AR-REEL7 C40c to +85c soic r-8
ad8698 rev. 0 | page 18 of 20 notes
ad8698 rev. 0 | page 19 of 20 notes
ad8698 rev. 0 | page 20 of 20 notes ? 2004 analog devices, inc. all rights reserved. trademarks and registered trademarks are the prop erty of their respective owners. d04807-0-4/04(0)

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